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1 low-noise 24-bit delta sigma adc ISL26102, isl26104 the ISL26102 and isl26104 provide a low-noise programmable gain amplifier along with a 24-bit delta-sigma analog-to-digital converter with two channel (ISL26102) or four channel (isl26104) differential, multiplexed inputs. the devices feature exceptional noise performance for conversion rates ranging from 2.5sps to 4ksps. the on-chip low-noise programm able-gain amplif ier provides gains ranging from 1 to 128, which supports 19.5mvfs from a 5v reference. the high input impedance allows direct connection of sensors such as load cell bridges to ensure the specified measurement accuracy without additional circuitry. the delta-sigma adc features a 3rd-order modulator providing up to 21.5 bit noise-free performance (10sps), with user-selectable word rates. the converter can be operated from an external clock source, an external crystal (typically 4.9152mhz), or the on-chip oscillator. the ISL26102 and isl26104 offer a simple-to-use serial interface. the ISL26102 and isl26104 are available in a thin shrink small outline package (tssop). the devices are specified for operation over the automotive temperature range (-40c to +105c). features ? programmable gain amplifier with gains of 1 to 128 ?low noise: 7nv/ hz @ pga = 128 ? linearity error: 0.0002% fs ? output word rates up to 4ksps ? low-side switch for load cell power management ? +5v analog and +2.7v to +5v digital supplies ? ISL26102 in 24 ld tssop ? isl26104 in 28 ld tssop ?esd 7.5kv - hbm applications ?weigh scales ? temperature monitors and controls ? load safety systems ? industrial process control ? pressure sensors related literature an1704 , ?precision signal path data acquisition system? ? adc pga 1, 2, 4, 8,16, 32, 64, 128 internal clock sdo/rdy sclk dvdd avdd dgnd dgnd xtalin/ clock vref+ external oscillator xtalout vref- ain1+ ain1- ain2+ ain2- ain3+ ain3- ain4+ ain4- input multiplexer isl26104 only cap cap sdi dgnd dgnd cs lsps agnd dvdd pwdn on-chip temp sensor figure 1. block diagram october 12, 2012 fn7608.0 caution: these devices are sensitive to electrostatic discharge; follow proper ic handling procedures. 1-888-intersil or 1-888-468-3774 | copyright intersil americas inc. 2012. all rights reserved intersil (and design) is a trademark owned by intersil corporation or one of its subsidiaries. all other trademarks mentioned are the property of their respective owners.
ISL26102, isl26104 2 fn7608.0 october 12, 2012 ordering information part number (notes 1, 2, 3) part marking description temp range (c) package (pb-free) pkg. dwg. # ISL26102avz 26102 avz 2 channel adc -40 to +105 24 ld tssop m24.173 isl26104avz 26104 avz 4 channel adc -40 to +105 28 ld tssop m28.173 isl26104av28ev1z evaluation board notes: 1. add ?-t*? suffix for tape and reel. please refer to tb347 for details on reel specifications. 2. these intersil pb-free plastic packaged products employ spec ial pb-free material sets, molding compounds/die attach materials , and 100% matte tin plate plus anneal (e3 termination finish , which is rohs compliant and compatible wi th both snpb and pb-free soldering opera tions). intersil pbfree products are msl classified at pb-free peak reflow temperat ures that meet or exceed the pb-free requirements of ipc/jede c j std-020. 3. for moisture sensitivity level (msl), please see device information page for ISL26102, isl26104 . for more information on msl please see techbrief tb363 . pin configurations ISL26102 (24 ld tssop) top view isl26104 (28 ld tssop) top view sdi sdo/rdy sclk dvdd avdd dgnd agnd ain1+ ain1- ain2+ ain2- xtalin/clock vref- xtalout dgnd cap cap dgnd vref+ pdwn 1 2 3 4 5 6 7 8 9 10 11 12 24 23 22 21 20 19 18 17 16 15 14 13 ISL26102 dvdd dgnd cs lsps cs sdi sdo/rdy sclk dvdd avdd dgnd agnd ain1+ ain1- ain2+ ain2- xtalin/clock vref- xtalout dgnd cap cap dgnd vref+ lsps pdwn 1 2 3 4 5 6 7 8 9 10 11 12 28 27 26 25 24 23 22 21 20 19 18 17 isl26104 ain3+ ain3- ain4+ ain4- 13 14 16 15 dvdd dgnd
ISL26102, isl26104 3 fn7608.0 october 12, 2012 pin descriptions (tssop) pin name pin number analog/digital input/output description ISL26102 isl26104 dvdd 1, 6 1, 6 digital digital power supply (2.7v to 5.25v) dgnd 2, 5, 7, 8 2, 5, 7, 8 digital digital ground xtalin/clock 3 3 digital/digital input external clock input: typically 4.9152mhz. tie low to activate internal oscill ator. can also use external crystal across xtalin/clock and xtalout pins. xtalout 4 4 digital external crystal connection cap 9, 10 9, 10 analog pga filter capacitor ain1+ 11 11 analog input positive analog input channel 1 ain1- 12 12 analog input negative analog input channel 1 ain3+ - 13 analog input positive analog input channel 3 ain3- - 14 analog input negative analog input channel 3 ain4- - 15 analog input negative analog input channel 4 ain4+ - 16 analog input positive analog input channel 4 ain2- 13 17 analog input negative analog input channel 2 ain2+ 14 18 analog input positive analog input channel 2 vref- 15 19 analog input negative reference input vref+ 16 20 analog input positive reference input agnd 17 21 analog input analog ground avdd 18 22 analog input analog power supply 4.75v to 5.25v lsps 19 23 digital output low-side power switch (open drain) cs 20 24 digital input chip select (active low) sdi 21 25 digital input serial data input pdwn 22 26 digital input device power down (active low) sclk 23 27 digital input serial port clock sdo/rdy 24 28 digital output data ready signal (conversion complete) and serial data output
ISL26102, isl26104 4 fn7608.0 october 12, 2012 absolute maximum rating s thermal information a gnd to d gnd . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.3v to +0.3v analog in to a gnd . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.3 to a vdd +0.3v digital in to d gnd . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.3 to d vdd +0.3v esd rating human body model (per mil-std-883 method 3015.7) . . . . . . . . . . . . .7.5kv machine model (per jesd22-a115). . . . . . . . . . . . . . . . . . . . . . . . . . 450v charged device model (per jesd22-c101) . . . . . . . . . . . . . . . . . . . . . . 2000v input current momentary . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 100ma continuous . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10ma latch-up (per jedec, jesd-78c; class 2, level a). . . .100ma @ +25c and +105c thermal resistance (typical) ja (c/w) jc (c/w) 24 ld tssop package (notes 4, 5) . . . . . . 65 18 28 ld tssop package (notes 4, 5) . . . . . . 63 18 maximum power dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 80mw maximum junction temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . .+150c maximum storage temperature range . . . . . . . . . . . . . .-65c to +150c operating conditions temperature range . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .-40c to +105c a vdd to a gnd . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4.75v to +5.25v d vdd to d gnd . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .2.7v to +5.25v caution: do not operate at or near the maximum ratings listed for extended periods of time. exposure to such conditions may adv ersely impact product reliability and result in failures not covered by warranty. notes: 4. ja is measured with the component mounted on a high effective thermal conductivity test board in free air. see tech brief tb379 for details. 5. for jc , the ?case temp? location is taken at the package top center. electrical specifications v ref + = 5.0v, v ref - = 0v, a vdd = 5v, d vdd = 5v xtalin/clock = 4.9152mhz (note 6) t a = -40c to +105c, unless otherwise specified. boldface limits apply over the operating temperature range, -40c to +105c. symbol parameter test level or notes min (note 7) typ max (note 7) units analog inputs v in differential input voltage range 0.5v ref / gain v input voltage range: common mode + signal gain = 1 a gnd + 0.1 a vdd - 0.1 v gain = 2, 4, 8, 16, 32, 64, 128 a gnd + 1.5 a vdd - 1.5 v input bias current; ain+, ain- gain = 1 300 na gain = 2, 4, 8, 16, 32, 64, 128 3 na input offset current; ain+, ain- gain = 1 20 na gain = 2, 4, 8, 16, 32, 64, 128 1 na system performance resolution no missing codes 24 bits inl integral nonlinearity gain = 1 0.0002 0.001 % fsr gain = 2 to 128 0.0004 % fsr offset gain = 1 0.4 ppm of fs offset drift gain = 1 300 nv/c gain = 2 to 128 300/gain 10 nv/c full scale error gain = 1 0.007 % gain = 2 to 128 0.02 % full scale drift gain = 1 0.1 ppm/c gain = 64 3.5 ppm/c gain = 128 3.5 ppm/c cmrr common mode rejection ratio gain of 1 85 110 db gain of 128 130 db psrr power supply rejection ratio gain of 1 100 db gain of 128 100 125 db owr output word rate (note 8) 2.5 4000 sps
ISL26102, isl26104 5 fn7608.0 october 12, 2012 voltage reference input vref voltage reference input vref = vref+ - vref- 1.5 5.0 a vdd + 0.1 v vref+ positive voltage reference input v ref- + 1.5 a vdd + 0.1 v vref- negative voltage reference input a gnd - 0.1 v ref+ - 1.5 v vrefi voltage reference input current 350 na low-side power switch r on on-resistance 10 continuous current 30 ma power supply requirements a vdd analog supply voltage 4.75 5.0 5.25 v d vdd digital supply voltage 2.7 5.0 5.25 v a idd analog supply current gain of 1 6 10 ma gain = 2 to 128 9 12 ma power-down 0.2 2.5 a standby 0.3 a d idd digital supply current gain of 1 750 950 a gain = 2 to 128 750 950 a power-down 1 26 a standby 1.8 a power normal gain = 1 33.75 54.75 gain = 2 to 128 48.75 64.75 mw power-down 6 w standby 10.5 w digital inputs v ih 0.7 d vdd v v il 0.2 d vdd v v oh i oh = -1ma d vdd - 0.4 v v ol i ol = 1ma 0.2 d vdd v input leakage current 10 a external clock input frequency 0.3 4.9152 mhz serial clock input frequency (note 9) 4 mhz notes: 6. if the device is driven with an external clock, best performance will be achieved if the rise and fall times of the clock are slowed to less than 20ns (10% to 90% rise/fall time). 7. compliance to datasheet limits is assured by one or more methods: production test, characterization and/or design. 8. output word rates (min and max in the table) are specified us ing 4.9152mhz clock. if a different clock frequency is used, or if the internal oscillator is used as the clock source for the converter, the output word rates will scale proportionally to the change in the clock frequ ency. 9. the owr (output word rate) setting dictates the rate at which the sdo/rdy signal will fall. to read every conv ersion word, reading of the conversion word should begin immediately after sdo/rdy falls and the sclk rate should be fast enough to read all 24 data bits of the conversion word before the next falling edge of sdo/rdy that indicates that a new co nversion word is available. electrical specifications v ref + = 5.0v, v ref - = 0v, a vdd = 5v, d vdd = 5v xtalin/clock = 4.9152mhz (note 6) t a = -40c to +105c, unless otherwise specified. boldface limits apply over the operating temp erature range, -40c to +105c. (continued) symbol parameter test level or notes min (note 7) typ max (note 7) units
ISL26102, isl26104 6 fn7608.0 october 12, 2012 table 1. input referred noise (nv, rms) output word rate (note 10) pga gain 1 2 4 8 16 32 64 128 2.5 187.1 101.8 52.0 25.0 14.5 8.8 6.6 6.5 5 209.2 112.2 55.9 28.5 16.3 10.5 8.4 8.2 10 253.6 133.0 63.8 35.5 20.0 13.9 11.9 11.6 20 308.3 157.7 77.6 43.8 25.0 18.1 15.7 15.2 40 417.7 207.1 105.1 60.2 35.1 25.3 23.3 22.4 80 547.2 264.6 140.1 78.2 46.8 34.9 31.6 30.1 100 607.0 292.7 159.4 87.5 52.2 39.7 35.4 34.3 160 780.3 368.2 203.0 110.6 68.0 52.3 46.2 45.2 200 845.1 405.5 222.2 119.7 74.2 57.3 50.6 49.5 320 1030.6 517.0 284.5 147.2 93.2 72.5 64.1 62.5 400 1169.0 591.7 318.1 165.3 105.2 81.9 72.6 70.5 640 1476.0 756.0 398.0 211.0 129.7 102.4 90.2 87.4 800 1632.0 857.9 445.0 237.2 139.5 114.7 101.0 98.9 1000 1806.1 958.6 489.5 267.0 157.8 126.8 112.4 107.7 1280 2018.0 1089.0 557.0 297.6 180.2 143.7 124.3 123.5 1600 2289.0 1234.0 632.0 328.0 202.3 163.4 134.0 132.0 2000 2572.5 1380.4 708.8 365.8 230.2 176.0 147.6 145.8 2560 2945.0 1538.0 801.0 423.7 259.0 201.0 162.3 161.3 3200 3287.0 1711.0 891.0 478.0 285.0 221.0 178.0 174.3 4000 3708.2 1876.9 955.1 545.1 316.6 242.8 196.0 194.9 note: 10. the adc has a programmable sinc 4 filter. the -3db bandwidth of the filter for a given word rate is 0.239 x owr. 1 10 100 1000 10000 1 10 100 1000 10000 word rate (sps) noise (nv rms ) 1x 2x 4x 8x 16x 32x 64x 128x figure 2. noise vs gain and word rate settings
ISL26102, isl26104 7 fn7608.0 october 12, 2012 table 2. noise free bits output word rate (note 11) noise-free bits 1 2 4 8 16 32 64 128 2.5 21.921.821.821.921.621.420.819.8 5 21.821.721.721.721.521.120.419.5 10 21.5 21.4 21.5 21.3 21.2 20.7 19.9 19.0 20 21.2 21.2 21.2 21.0 20.9 20.3 19.5 18.6 40 20.8 20.8 20.8 20.6 20.4 19.8 19.0 18.0 80 20.4 20.4 20.4 20.2 19.9 19.4 18.5 17.6 100 20.3 20.3 20.2 20.0 19.8 19.2 18.4 17.4 160 19.9 20.0 19.8 19.7 19.4 18.8 18.0 17.0 200 19.8 19.8 19.7 19.6 19.3 18.7 17.8 16.9 320 19.5 19.5 19.3 19.3 19.0 18.3 17.5 16.5 400 19.3 19.3 19.2 19.1 18.8 18.1 17.3 16.4 640 19.0 18.9 18.9 18.8 18.5 17.8 17.0 16.0 800 18.8 18.8 18.7 18.6 18.4 17.7 16.8 15.9 1000 18.7 18.6 18.6 18.4 18.2 17.5 16.7 15.7 1280 18.5 18.4 18.4 18.3 18.0 17.3 16.5 15.5 1600 18.3 18.2 18.2 18.1 17.8 17.1 16.4 15.5 2000 18.2 18.1 18.0 18.0 17.7 17.0 16.3 15.3 2560 18.0 17.9 17.9 17.8 17.5 16.8 16.2 15.2 3200 17.8 17.8 17.7 17.6 17.3 16.7 16.0 15.1 4000 17.6 17.6 17.6 17.4 17.2 16.6 15.9 14.9 note: 11. noise-free resolution in table 2 is calculated as log ((input span)/(rms noise x 6.6))/log(2). the result is rounded to the nearest tenth of a bit. the input span is equivalent to 0.5vref/gain, v ref = 5v. the rms noise is selected from table 1 for the desired output word rate and gain option. 0 2 4 6 8 10 -40 -10 20 50 80 110 temperature (c) current (ma) normal mode figure 3. analog current vs temperature (gain = 2 to 128) 1 10 100 1000 10000 -40 -10 20 50 80 110 temperature (c) current (a) normal mode, all pga gains powerdown mode figure 4. digital current vs temperature
ISL26102, isl26104 8 fn7608.0 october 12, 2012 typical characteristics figure 5. noise spectral density, 4ksps, pga gain = 1 figure 6. noise spectral density, 4ksps, pga gain = 128 1 10 100 1000 0.1 1 10 100 1000 frequency (hz) noise (nv/ hz) 1 10 100 0.1 1 10 100 1000 frequency (hz) noise (nv/ hz) ain1+ ain2+ ain1- ain2- avdd temp sensor + - + - 3 rd order ? modulator programmable digital filter serial port 2x, 4x, 8x, 16x 32x, 64x, 128x 100nf cap cap 390 390 1x 1x figure 7. ISL26102 (2 channel) block diagram
ISL26102, isl26104 9 fn7608.0 october 12, 2012 circuit description a key element in the ISL26102/isl26104 a/d converters is its low noise chopper-stabilized programmable gain amplifier. the amplifier features seven gain settings (2x, 4x, 8x, 16x, 32x, 64x, and 128x). on these gain settings, the amplifier has very high input impedance but has restrict ed common mode range, which does not extend all the way to the power supply rails. when the gain of 1x is selected, the chopper-stabilized amplifier is bypassed. the modulator input, which is used directly in 1x gain, has a common mode range that extends to the supply rails. but, because of this greater common mode range on the 1x gain setting, the input current is hi gher than on the other gain settings. the ISL26102 provides the user with two fully differential signal inputs at the multiplexer plus two other internal channel selections, which allow the user to monitor the analog supply voltage of the chip, and the on-chip temperature sensor. the isl26104 provides the user with two additional fully differential inputs on the multiplexer. the programmable gain amplifier has a passive rc filter on its output. the resistors are located in side the chip on the outputs of the differential amplifier stages. the capacitor (nominally a 100nf c0g ceramic or pps film (polyphenylene sulfide)) for the filter is connected to the two cap pins of the chip. the outputs of the differential amplifier stages of the pga are filtered before their signals are presented to the delta-sigma modulator. this filter reduces the amount of noise by limiting the signal bandwidth and eliminating the cho pping artifacts of the chopped pga stage. figure 7 illustrates a block diagram of the programmable gain amplifier. functional description analog input span the input span of the a/d converter is determined by the magnitude of the voltage reference and the gain setting selection. the voltage reference magnitude is determined by the voltage difference between the vref+ and the vref- pins. this voltage may be as low as 1.5v or as great as the analog supply voltage to the chip. the voltage on the vref pins is scaled to accept a voltage into the a/d converter on 1x gain of 0.5 vref/gain where gain is 1. an illustration of the input span when using a 5v v ref is in figure 8. the figure illustrates that with a v ref = 5v and a gain setting of 1x, the input span will be 2.5v, which is a fully differential signal. if the programmable gain amplifier gain is set to another value other than 1x, the input span will be reduced by the gain scale factor. with a v ref = 5v and the pga gain set at 128x, the input span into the adc will be [(0.5)5v]/128 = 19.53mv on a fully differential basis. digital filter the output of the delta-sigma modulator in the a/d converter is filtered with a sinc 4 digital filter that includes programmable decimation to achieve a wide range of output word rates. the transfer function of the sinc 4 filter is illustrated in figure 9. figure 9 is normalized to 1 be ing the output word rate. the output word rate can be select ed by setting bits in the owr (output word rate) register. the converter provides a wide selection of word rates as shown in table 3. note that the word rates are based upon an xtalin /clock of 4.9152mhz. if the clock is a different frequency than 4.9152mhz, the actual output word rate will scale proportionally. table 3. output word rate register settings data rate (sps) register code (hex) 2.5 00 501 10 02 20 03 40 04 80 05 100 0b 160 06 200 0c 320 07 400 0d 640 08 800 0e 1000 11 1280 09 1600 0f 2000 12 2560 0a 3200 10 4000 13 2.50 4.50 1.00 0.00 3.00 ain+ ain- vcm 2.500 2.500 0.50 2.00 1.50 3.50 4.00 5.00 figure 8. differential input for v ref = 5v, gain = 1x
ISL26102, isl26104 10 fn7608.0 october 12, 2012 digital filter settling time if the input mux selection register is written into to select a new channel, the modulator and the digital filter are reset and the converter begins computing a new output word when the new mux selection is made. the first conversion word output from the a/d after a new mux channel is sele cted, or after the pga gain is changed, will be delayed to allow the filter to fully settle. a sinc 4 filter takes four conversion times to fully settle, therefore the sdo/rdy signal will not fall until a time of four normal conversion periods has elapsed. the sdo/rdy output falls to signal that an output conversi on word is ready to be read. whenever the input signal has a la rge step change in value, it may take as many as six output conversions for the output word to accurately represent the new input value. clock sources the ISL26102/isl26104 can operate from an internal oscillator, and external clock source, or from a crystal connected between the xtalin/clock and xtalout pins. see the block diagram for the clock system in figure 10. when the converter is powered up, the clock detect block determines if an external clock source is present. if a clock signal grea ter than 300khz is present on the xtalin/clock pin, the circuitry will disable the internal oscillator and use the external clock as the clock to drive the chip circuitry. if the adc is to be operated from the internal oscillator the xtalin/clock pin should be grounded. if the adc is to be driven with an external clock there should be a 100 resistor placed in series with the clock signal to the xtalin/clock pin. this helps slow the rise and fall time edges, which can impact converter performance. if the adc is to be operated with a crystal, the crystal should be located very close to the a/d converter package pins. note that loading capacitors for the crystal are not required as there are loading capacitors built into the silicon, although the capacitor values are optimized for operation with a 4.9152mhz crystal. overview of registers and a/d converter operation the ISL26102, isl26104 devices are controlled via their serial port by accessing various on-chi p registers. communication to the a/d via the serial port occurs by writing a command byte followed by a data byte. all registers in the converter are accessed or written as 8-bit wide registers, even though some data words may be up to three bytes in length. the converter has offset registers (three bytes wide) associated with each pga gain setting. these registers hold the offset calibration word, a three byte twos complement word, for each gain selection. when power is first applied to the converter these registers are reset to zero. note that the ISL26102, isl26104 converters do not have gain calibration registers for the pga gains. this is because the gain for each pga gain setting is calibrated at the factory. table 4 list the registers inside the adc. when power is first applied the offset array registers, registers which hold the offset calibration words for each pga gain, are set to zero. the chip id register has a bit, which allows the user to identify whether the chip is an ISL26102 (2 channel) or an isl26104 (4 channel) device. this register also has a code, which is assigned to reveal the revision of the chip. the sdo/lsps register allows the user to control the behavior of the sdo (serial data output) output. if bit (b1) is set to logic 0, the sdo/rdy output will go low when conversions are completed and output the 24-bit conversion word if cs is taken high and 24 sclks are issued to the sclk pin. if the sdo bit in this register is set to logic 1, the sdo output will be set to a tri-state condition (high output impedance). this allows another device, such as another a/d converter, to be connected to this same signal line going to the microcontroller. the lsps (low-side power switch) bit allows the user to toggle a switch via the lsps pin that can be used to enable power to a load cell or other circuitry. when the lsps bit is logic 0 the lsps switch is open. when the lsps bit is logic 1, the switch is closed. the lsps bit is set back to a logic 0 if the chip is put into standby via the standby register, or if the pdwn signal is activated. see data sheet tables for the curre nt capability of the switch. the standby register has a bit which when set to logic 1, the chip enters the standby mode. in standby mode, the chip enters a low power state. only the crystal oscillator is left powered (if used) to enable a quick return to full operat ion when bit (b0) is set back to logic 0. if the crystal is not being used, it is not powered. in this figure 9. transfer function of sinc 4 normalized to 1 = output word rate attenuation (db) normalized frequency (1.00 = owr) -140 -180 -200 -160 -120 -100 -80 -60 -40 -20 0 0.10 1.00 10.00 figure 10. clock generator block diagram xtalin/ crystal oscillator xtalout to adc internal oscillator clock detect mux en clock
ISL26102, isl26104 11 fn7608.0 october 12, 2012 case, there is no difference in power consumption for standby or power-down modes. the output word rate register allows the user to set the rate at which the converter performs conversions. table 3 lists the output word rate options. the input mux selection register defines the input signal that will be used when conversions are performed. the signals include either 2 (ISL26102) or 4 (isl2610 4) differential input channels, an on-chip temperature sensor, or the monitor node for the avdd supply voltage. note that if th e temperature sensor or the avdd monitor are selected the pga gain is internally set for 1x gain. the pga gain register allows the user to set the pga gain setting for the channel pointed to by the channel pointer register. the pga provides gain settings of 1x (in this gain setting the programmable gain amplifier is actually bypassed and the signal goes directly to the modulator), 2x, 4x, 8x, 16x, 32x, 64x, and 128x. the conversion control register provides the means to initiate offset calibration, or initiate sing le or continuous conversions. if bit b2 of this register is set to a logic 1, an offset calibration will be performed and the states of bits b1 and b0 are ignored. the state of bit b2 will be set back to a logic 0 after the offset calibration is complete. if the b1b0 bits are set to 01, a single conversion will be performed. when the conversion is completed, the bits will be set back to 00, the sdo/rdy pin will be taken low (note that the cs pin must be a logic 1 for sdo/rdy to fall) and the conversion data will be held in a register. if the user enables cs (held at logic 1) and provides 24 sclks to the sclk pin, the data word will be shifted out of the sdo/rdy pin as a 24-bit two?s complement word, starting with the msb. data bits are clocked out on the rising edge of sclk. if the entire 24-bit data word is not read before the completion of the next conversion, it will be overwritten with the new conversion word. if the b1b0 bits are set to 10 , conversions will be performed continuously until bits b1b0 are set to either 00 or 01, standby mode is activated, or the pdwn pin is taken low. refer to ?reading conversion data? on page 14. the delay timer register allows the user to program a delay time, which will be inserted between the time that the user selects an input to be converted via the input mux selection register and when the conversion is started. if continuous conversions are selected via the conversion control register, the input mux selection register can be chan ged without needing to stop conversions. the delay timer regist er allows the user to insert a delay between when the mux is changed and when a new conversion is started. if the dela y timer register is set to all 0's the minimum dela y will be 100s. any time the pga gain setting is changed, the channel selection is changed, or a command is gi ven to start conversion(s), the user can expect a delay before the sdo/rdy signal will fall. this delay is defined by equation 1: the first 4ms is for the pga to settle. this delay cannot be changed. the delay timer register setting is user controllable, and it dictates the majority of th e second section of the equation. the 4*(1/owr) term is the time requ ired for the filter to settle at the owr (output word rate), which has been selected in the output word rate register. the pga offset array registers hold the calibration results for the offset calibration done for each of the pga gain settings. the result of an offset calibration is a 24-bit twos complement word. there are eight high byte registers, eight mid byte registers and eight low byte registers. when reading or writing to one of the pga offset array byte registers, the register selected will be determined by the pga pointer register. the pga pointer register contains the pointer to the pga offset register array bytes associated with a specific pga gain. 4ms delay timer register setting ? 4ms () 100 s ) 4 ? 1owr ? () +++ [] (eq. 1)
ISL26102, isl26104 12 fn7608.0 october 12, 2012 table 4. control registers name address data bits notes write read b7 b6 b5 b4 b3 b2 b1 b0 registers are accessed by address byte followed by register data byte chip id n/a 00h b4 0 = isl26104 1 = ISL26102 b3-b0 revision code sdo/lsps 82h 02h b1 1= disable sdo 0 = enable sdo b0 1 = lsps on 0 = lsps off 0 is default 0 is default standby 83h 03h b0 1 = enable standby 0 = disable 0 is default output word rate 85h 05h see table 3 on page 9 0 is default, 2.5sps input mux selection 87h 07h isl26104 b2 b1 b0 000 = channel 1 001 = channel 2 010 = channel 3 011 = channel 4 100 = analog supply monitor 101 = temperature sensor 110 = not used 111 = not used ISL26102 b2 b1 b0 000 = channel 1 001 = channel 2 010 = analog supply monitor 011 = temperature sensor 100 = not used 101 = not used 110 = not used 111 = not used channel pointer 88h 08h isl26104 b2 b1 b0 000 = channel 1 001 = channel 2 010 = channel 3 011 = channel 4 100 = analog supply monitor 101 = temperature sensor 110 = not used 111 = not used ISL26102 b2 b1 b0 000 = channel 1 001 = channel 2 010 = analog supply monitor 011 = temperature sensor 100 = not used 101 = not used 110 = not used 111 = not used
ISL26102, isl26104 13 fn7608.0 october 12, 2012 writing to on-chip registers writing into a register on the ch ip involves writing an address byte followed by a data byte. the lead bit of the address byte is always a logic 1 to indicate that data is to be written. the remaining seven bits of the addr ess byte contain the address of the register that is to be written. to begin the write cycle, cs must first be taken low with sclk low. this should occur at least 125ns before sclk goes high. this is shown as t cs in the timing diagram of figure 11. once cs is low, the user must then present the lead bit to the sdi port. the data bits will be latched into the port by rising edges of sc lk. the data set-up time (t ds ) of the data bits to the rising edge of sclk is 50ns (note that one half clock cycle of the highest sclk rate is 1/(2*4 mhz) = 125ns). data hold time (t dh ) is also 50ns. data bits should be advanced to the next bit on falling edges of sclk. once the eight data bits have been written, cs should be returned to high. (cs must be high to read conversion data words from the port). when cs goes high the user should ignore any activity on the sdo/rdy pin for at least 10 cycles of the master clock, which is driving the adc. see figure 11 for an illustration of the timing to write on-chip registers. if multiple registers are to be written, cs should be taken high after each address byte/data byte combination an d remain high for at least a period of time eq ual to 6*1/(xtal/clock) frequency. if the chip is operating from a 4.9152mhz master clock, this would mean that cs should remain high between write cycles for at least 6*1/4.9152mhz = 1.22s. lower frequency master clock rates (minimum master clock rate can be as low as 300khz) will require cs to remain high for a longer period of time between register write cycles. each time an address/data byte combination is written into the port, the master clock is used to place the data into the register after cs returns high. this is requir ed because the data transfer must be synchronized to the clock that is driving the modulator/filter circuitry. reading from on-chip registers reading from a register on the ch ip begins by writing an address byte into the sdi port. the lead bit of the address byte is always a pga gain 97h 17h b2 b1 b0 000 = 1x 001 = 2x 010 = 4x 011 = 8x 100 = 16x 101 = 32x 110 = 64x 111 = 128x pga gain setting for channel pointed to by the channel pointer register. whenever the analog supply monitor or the temp sensor are selected, the pga gain is set to 1x. conversion control 84h 04h b2 0 = off 1 = perform offset calibration b1 b0 00 = stop conversions 01 = perform single conversion 10 = perform continuous conversions 11 = not used performing offset calibration has priori ty over instructions from bits b1b0 delay timer c2h 42h b7-b0 the start of conversion is delayed by: delay = register word*4ms + 100s pga offset array (high byte) bdh 3dh offset calibration result most significant byte for pga pointed to by pga pointer register pga offset array (mid byte) beh 3eh offset calibration result middle byte for pga pointed to by pga pointer register pga offset array (low byte) bfh 3fh offset calibration result low byte for channel pointed to by channel pointer register pga monitor bch 3ch b2 b1 b0 000 = 1x 001 = 2x 010 = 4x 011 = 8x 100 = 16x 101 = 32x 110 = 64x 111 = 128x this register points to the offset regist er associated with the pga gain selection table 4. control registers (continued) name address data bits notes
ISL26102, isl26104 14 fn7608.0 october 12, 2012 logic 0 to indicate that data is to be read from an on-chip register. the remaining seven bits of the address byte contains the address of the register that is to be read. to begin the read cycle, cs must first be taken low with sclk low and be low for at least 125ns before sclk is taken high to latch the first data bit. the eight address bits will be latched into the port by rising edges of sclk. the data set-up time (t ds ) of the data bits to the rising edge of sclk is 50ns (one half clock cy cle of the highest sclk rate is 1/(2*4mhz) = 125ns). data hold time (t dh ) is also 50ns. address bits should be advanced to the next bit on falling edges of sclk. once the address byte has been written, the port will output a byte from the selected 8-bit register onto the sdo pin. a total of 16 sclks are required to write the address byte and then read the 8-bit register output. the timing for reading from on-chip registers is illustrated in figure 12. reading conversion data reading conversion data is done in a different manner than when reading on-chip registers. after writing into the conversion control register to instruct the a/d to start conversions, the user will then wait for the sdo/rdy signal to fall. once the sdo/rdy signal falls, the 24-bit conversion data word becomes available to the port. to read the conversion word, the cs signal should be left in the logic 1 state and 24 sclks issued to the sclk pin. the first rising sclk edge will make the msb data bit of the 24-bit word become available. the falling edge of the first sclk will latch the bit into the external receiving logic device. subsequent rising edges of sclk will cause the port output to advance to the next data bit. once the last data bit is read, the sclk signal should remain low until another conversion word is available or until a command to write or read an on-chip register is performed. sdo/rdy goes low to signal that a conversion has been performed and that the conversion word is available. if the analog input signal goes over range this may cause the modulator to become unstable. if this condition occurs the modulator resets itself. the output code will be held at full scale but the effect of the modulator being reset will cause the sdo/rdy signal to fall at only one fourth of its word rate. this occurs because when the modulator is reset, the digital filter is also reset and it takes four conversion periods for the filter to accumulate enough modulator bit stream information to produce an accurate conversion result. figure 11. write on-chip register waveforms cs sclk sdi 12 345 67891 0 111 1 11 123456 aaa aaaaddd ddddd 654 32 107 65 4321 0 don?t care don?t care t ds t dh w t cs t sc figure 12. read on-chip register waveforms 12345 6 78 911 11 111 01 23 456 aaa aa aax x xx x xx xx x x x x x x x x x 0 1 2 3 4 5 6 x x qqqqqqqx x q 7654 3210 don?t care cs sclk sdi sdo xx (don?t care) t cs t sc r t ds t dh figure 13. reading conversion data word waveforms sdo/rdy sclk data ready new data ready data msb lsb 222 0 321 3 12 2 4 4 cs
ISL26102, isl26104 15 fn7608.0 october 12, 2012 output data format the converter outputs data in twos complement format in accordance with coding shown in table 5. operation of pdwn when power is first applied to the converter, the pdwn pin must transition from low to high after both power supplies have settled to specified levels in order to initiate a correct internal power-on reset. a means of controlling the pdwn pin with a simple rc delay circuit is illustrated in figure 14. if avdd and dvdd are different supplies, be certain that avdd is fully established before pdwn goes high. the pdwn pin can be taken low at any time to reduce power consumption. when pdwn is taken low, all circuitry is shut down, including the crystal oscillator. when coming out of power-down, pdwn is brought high to resume operation. there will be some delay before the chip begins operation. the delay will depend upon the source of the clock being used. if the xtalin/clock pin is driven by an external clock, the delay will be minimal. if the crystal oscillator is the clock source, the oscillator must start before the chip can function. using the on chip crystal oscillator amplifier with an attached 4.9152mhz clock will typically require about 20ms to start-up. standby mode operation the a/d converter can be placed in the standby mode by writing to the standby register. standby mode causes the converter to enter a low power state except for the crystal oscillator amplifier. if the converter is operated with a crystal connected to the xtalin/clock and xtalout pins the crystal will continue to oscillate. this reduces start-up time when the standby register bit is written back to logic 0 to exit standby mode. low side power switch the adc includes a low side power switch. the lsps pin is an open drain connection to a transi stor, which can be turned on or off via bit control in the sdo/lsps register. the lsps switch can be used to enable/disable excitation to external systems, such as a load cell. figure 15 illustrate s the typical connection of the adc in a load cell measurement system. the lsps pin is connected to the low side of the load cell. table 5. output codes corresponding to input input signal description output code (hex) + 0.5v ref /gain + over-range 7fffff 0.5v ref /[gain*(2 23 - 1)] + 1 lsb 000001 0 zero input 000000 -0.5v ref /[gain*(2 23 -1)] - 1 lsb ffffff - 0.5v ref /gain - over-range 800000 figure 14. pdwn delay circuit dvdd 1k ? 2.2nf connect to pdwn pin avdd vref+ cap cap ain1+ ain1- ain2+ ain2- vref- agnd dgnd xtalout pdwn sclk sdo/rdy dvdd ISL26102 xtalin/clock + - 0.1f micro controller 16 9 10 11 12 15 17 3 4 22 23 24 gain = 128 3.3v 5v 0.1f 18 figure 15. a load cell measuremen t application using the ISL26102 lsps cs sdi 13 14 19 2, 5, 7, 8 20 21 16
ISL26102, isl26104 16 fn7608.0 october 12, 2012 device supply and temperature monitoring one of the multiplexer input select ions is the avdd monitor. this option allows the a/d converter to measure a divided down value of the avdd voltage. the nominal output code from avdd monitor is given by (2 23 )*avdd/(2*vref). table 6 provides a listing of the nominal count of the a/d converter associated with supply voltage values between 4.75 and 5.25v. table 6 is based on v ref = 5v. if a v ref of 2.5v is used, the output code from the a/d converter will stay at +full scale when avdd > 5v. thus, the avdd monitor will not be able to check the voltages greater than 5v, but it will provide proper readings for avdd voltages below 5v. when the input mux selection regist er is instructed to select the on-chip temperature sensor signal, the a/d measures a differential voltage produced between two diodes that are biased at different operating currents. the differential voltage is defined by equation 2: whenever the temperature sensor is selected in the input mux selection register, the gain is set to 1x. at a temperature of +25c th e measured voltage will be approximately 111.7mv. the ac tual output code from the converter will depend upon the magnitude of the vref signal. the 111.7mv signal will be a portio n of the span set by the vref voltage using a gain setting of 1x. if v ref is 5v, one code in the converter will be 0.5(v ref )/2 23 = 298nv. since the converter span is bipolar, and its span represents 8.338 million codes, the +111.7mv will output of a code of approximately 374,800 counts. the on-chip temperature will typically be about 3 hotter than ambient because the device's power consumption is about 50 mw and the thermal impedance from die to ambient is about 63/w; (0.05)*63 = 3.15. getting started when power is first applied to the converter, the pdwn pin should be held low until the power supplies and the voltage reference are stable. then pdwn should be taken high. when this occurs the serial port logic and other logic in the chip will have been reset. the chip contains factory calibration data stored in on-chip non-volat ile memory. when pdwn goes positive this data is transferred into the appropriate working registers. this initialization can take up to 12.6 ms. if an external clock or the internal oscillator are used as the clock for the chip, then this 12.6ms time includes the time necessary for these to be functional. but, if the crystal oscillator is used, the crystal may take 20ms to start up before the 12.6ms initialization occurs. writing into or reading from the serial port should be delayed until the clock source and the initialization period have elapsed. once the clock source and initialization period have elapsed, the user should configure the adc by writing into the appropriate registers. the commands and the corresponding data bytes that are to be placed into each of the registers are shifted into the sdi pin with cs held low. cs should be taken high for at least six cycles of the master clock after each command/data byte combination. this allows the cont rol logic to properly synchronize the writing of the register with the master clock that controls the modulator/filter system. each command/data byte combination should have its own cs cycle of cs going low, shifting the data, then cs going high, and remaining high for at least six cycles of the master clock. even though the device has been powered up, reset, and its register settings have been conf igured, the programmable gain amplifier and modulator portions of the adc remain in a low power state until a command to start conversions is written into the conversion control register. to minimize drift in the device due to self-heating, it is recomm ended that after all registers are initialized to their initial co ndition, the command to start continuous conversions be issued as soon as is practical. subsequent changes to registers, such as selecting another mux channel, should be performed with continuous conversions active. the proper method of writing to the other registers when continuous conversions are active is to wait for sdo/rdy to fall, read the conversion data, then take cs low and issue the command and the data byte that is to be written into a register, then return cs high. if multiple registers are to be written, cs should be toggled low and high to frame each command/data byte combination. whenever any of the following registers [sdo/lsps, output word rate, input mux selection, pga gain, delay timer, pga offset array, or offset calibration] are written with continuous conversions in prog ress, the digital filter will be reset and there will be a delay determined by equation 1 on page 11. the delay will begin when cs returns and remains high. when the delay has elapsed, the sdo/rdy signal will go low to table 6. analog supply monitor output codes over supply voltages (v ref = 5.0v) avdd (v) output code (5%) 5.25 4407063 5.10 4281464 5.00 4197996 4.90 4114662 4.75 3989915 figure 16. input multiplexer block diagram ain1 ain1 ain2 ain2 ain3 ain3 ain4 ain4 to buffer/pga 24-bit adc + - temp sensor avdd + - + - + - + - (eq. 2) v = 102.2 mv + (379v* t(c))
ISL26102, isl26104 17 fn7608.0 october 12, 2012 signal that a conversion data wo rd is available. the chip id register (read only), the channel pointer register, and the pga monitor register can be read or written without any effect to the filter, and therefore there will be no delay in sdo/rdy falling. if the standby register is enabled, conversions will be stopped. performing calibration the offset calibration function in the a/d converter removes the offset associated with the pga (programmable gain amplifier) in a specific gain setting. there are eight gain settings (1x, 2x, 4x, 8x, 16x, 32x, 64x, and 128x) and there is an array of eight sets of three byte registers which hold the high, middle, and low bytes of a 24-bit calibration word. the word is stored in twos complement format. when calibration is performed it is to correct the pga offset and is not actually associated with a given input channel. when a calibration is executed, its result is based upon the results of the converter performing a conversion with the input to the pga shorted internally to the chip. the conversion result will have an uncertainty due to the peak-to-peak noise of the converter on the word rate in which the calibration is performed. lower word rates have lower signal bandwidth and therefore will have less peak to peak variation in the output result when a calibration is performed. therefore, it can improve calibration accuracy if the calibration is performed with the lowest word rate acceptable to the user. perform a pga offset calibration 1. write to the output word rate register (85h) and select a word rate. 2. write to the input mux selection register (87h) and select an input channel (ain1 to ain4, not avdd monitor or temperature sensor). note that the channel will actually be shorted internally so it need not be a specific channel. 3. write to the channel pointer register (88h) with the same selection written into the mux selection register. 4. write the pga gain selection into the pga gain register (97h). 5. write bits b1 and b0 of the conversion control register (84h) setting b1 to logic 1 and bit b2 to logic 0 to perform continuous conversions. 6. allow some delay and then write bit b2 of the conversion control register (84h) to logic 1 to st art the calibration process. the calibration time will be a function of the selection made in the output word rate register. to determine when the calibration cycle is completed the user has two options. one is to monitor sdo/rdy for a falling edge as this signals the completion of conversion. a second approach would be to introduce a wait timer for at least the period of five conversion times at the word rate selected. [example: if the word rate is 10sps the calibration should be completed at 5x 1/10s or 500ms. after this time, the microcontroller can poll bit 2 of the conversion control register. bit b2 will be set back to logic 0 when the calibration has completed. it is best not to poll the register continuously because the added activity on the serial port may introduce noise and impact the calibration result. read offset calibration registers after an offset calibration has been performed, the calibration result, which is a 24-bit (3 bytes) two's complement word, is stored in the pga offset arrays. some user applications prefer to calibrate their system in the factory, then off load the calibration data and write it into non-volatile memory. then when the product is powered up, this data is written back into the registers of the adc. 1. write into the pga pointer register (bch) the selection wanted for the gain of the pga. 2. read the three different pga offset array registers, high byte (3dh), mid byte(3eh), and low byte(3fh). note that they can be read in any order, just understand that the three bytes represent a two's complement 24-bit word with the byte in order, high, mid and low. write offset calibration registers upon power-up the offset registers are initialized to zero. after an offset calibration is performed th e registers associated with that selected pga gain will contain a valid 24-bit two's complement number. this number can be saved into non-volatile memory and then written back to the pga offset array register. 1. write into the pga pointer register (bch) the selection for the gain setting of the pga for which offset data is to be written. 2. write the three different pga offset array registers, high byte (bdh), mid byte (beh), and low byte (bfh). note that they can be written in any order, just understand that the three bytes represent a two's complement 24-bit word with the byte in order, high, mid and low. the value written will be subtracted from the conversion data before it is output from the converter wh enever that particular pga gain setting is used. offset values up to the equivalent of full scale of the converter can be written but realize that this can consume dynamic range for the actual signal if the offset value is set to a large number. example command sequence table 7 illustrates an example command sequence to set up the adc once power supplies are active. the sequence of commands, set channel pointer, set pga gain setting, set mux selection, set data rate, and start continuous conversions, can be written into the adc as a sequence, each framed with cs going low at the beginning of each command and re turning high at the end of the associated data byte (the rising edge of cs is the signal that actually writes the data byte to the control register). after continuous conversions are started, it is best if a time delay occur before the perform offset calibration is issued . there is no specific amount of delay time as this depends upon th e gain selection and the accuracy required. when the command to perform the offset calibration is issued, the continuous conversions in progress will be paused and the conversion sequence will be performed as necessary to perform the calibration. once the calibrat ion is completed, continuous conversions will be automatically restarted. any subsequent commands which write into registers [sdo/lsps, output word rate, input mux selection, pga gain, delay timer, pga offset array, or offset calibration] while continuous conversions are in progress will reset the digital filter and introduce a delay determined by equation 1 on page 11, after which, the sdo/rdy signal will toggle low to signal the availability of a conversion word.
ISL26102, isl26104 18 fn7608.0 october 12, 2012 table 7. example command sequence operation register address (write) data comments set channel pointer channel pointer 88h 01h set to select channel 2 (ain2+, ain2-) set pga gain setting pga gain 97h 06h sets pga gain to 64x. this pga gain is applied to the signal channel pointed to by the channel pointer set above. set mux selection input mux selection 87h 00h mux selection dete rmines which channel is connected to the adc. this step selects mux input 1 (ain1+, ain1-). set data rate owr 85h 11h sets output word rate to 1ksps. see table 3 for other data rate options. start continuous conversions conversion control 84h 02h set bits (b1-b0) of the conver sion control register to ?10? to start continuous conversions. perform offset calibration conversion control 84h 04h set bit (b2) of the conversi on control register to 1 to initiate an offset calibration of the pga gain setting selected above. note that bit (b3) will return to 0 when the calibration is completed. set mux selection input mux selection 87h 01h mux selection determines which channel is connected to the adc. this step selects mux input 2 (ain2+, ain2-).
ISL26102, isl26104 19 intersil products are manufactured, assembled and tested utilizing iso9000 quality systems as noted in the quality certifications found at www.intersil.com/en/suppor t/qualandreliability.html intersil products are sold by description only. intersil corporat ion reserves the right to make changes in circuit design, soft ware and/or specifications at any time without notice. accordingly, the reader is cautioned to verify that data sheets are current before placing orders. information furnished by intersil is believed to be accurate and reliable. however, no responsi bility is assumed by intersil or its subsid iaries for its use; nor for any infringem ents of patents or other rights of third parties which may result from its use. no license is granted by implication or otherwise under any patent or patent rights of i ntersil or its subsidiaries. for information regarding intersil corporation and its products, see www.intersil.com fn7608.0 october 12, 2012 for additional products, see www.intersil.com/en/products.html products intersil corporation is a leader in the design and manufacture of high-performance analog semico nductors. the company's product s address some of the industry's fastest growing markets, such as , flat panel displays, cell phones, handheld products, and noteb ooks. intersil's product families address power management and analog sign al processing functions. go to www.intersil.com/products for a complete list of intersil product families. for a complete listing of applications, re lated documentation and related parts, plea se see the respective product information page. also, please check the product information page to ensure that you have the most updated datasheet: ISL26102, isl26104 to report errors or suggestions for this datasheet, please go to www.intersil.com/askourstaff fits are available from our website at http://rel.intersil.com/reports/search.php revision history the revision history provided is for informational purposes only and is believed to be accurate, but not warranted. please go t o web to make sure you have the latest revision. date revision change october 12, 2012 fn7608.0 initial release.
ISL26102, isl26104 20 fn7608.0 october 12, 2012 package outline drawing m24.173 24 lead thin shrink small outline package (tssop) rev 1, 5/10 detail "x" typical recommended land pattern top view side view end view dimension does not include mold flash, protrusions or gate burrs. mold flash, protrusions or gate burrs shall not exceed 0.15 per side. dimension does not include interlead flash or protrusion. interlead flash or protrusion shall not exceed 0.25 per side. dimensions are measured at datum plane h. dimensioning and tolerancing per asme y14.5m-1994. dimension does not include dambar protrusion. allowable protrusion shall be 0.08mm total in excess of dimension at maximum material condition. minimum space between protrusion and adjacent lead is 0.07mm. dimension in ( ) are for reference only. conforms to jedec mo-153. 6. 3. 5. 4. 2. 1. notes: 7. 5 seating plane c h 3 2 1 24 b 12 1 3 13 a plane gauge 0.05 min 0.15 max 0-8 0.60 0.15 0.90 1.00 ref 0.25 see detail "x" 0.15 0.25 (0.65 typ) (5.65) (0.35 typ) (1.45) 6.40 4.40 0.10 0.65 1.20 max pin #1 i.d. mark 7.80 0.10 +0.05 -0.06 -0.06 +0.05 -0.10 +0.15 0.20 c b a 0.10 c - 0.05 0.10 c b a m
ISL26102, isl26104 21 fn7608.0 october 12, 2012 package outline drawing m28.173 28 lead thin shrink small outline package (tssop) rev 1, 5/10 detail "x" typical recommended land pattern top view side view end view dimension does not include mold flash, protrusions or gate burrs. mold flash, protrusions or gate burrs shall not exceed 0.15 per side. dimension does not include interlead flash or protrusion. interlead flash or protrusion shall not exceed 0.25 per side. dimensions are measured at datum plane h. dimensioning and tolerancing per asme y14.5m-1994. dimension does not include dambar protrusion. allowable protrusion shall be 0.08mm total in excess of dimension at maximum material condition. minimum space between protrusion and adjacent lead is 0.07mm. dimension in ( ) are for reference only. conforms to jedec mo-153. 6. 3. 5. 4. 2. 1. notes: 7. 5 seating plane c h 3 2 1 28 b 14 1 3 15 a plane gauge 0.05 min 0.15 max 0-8 0.60 0.15 0.90 1.00 ref 0.25 see detail "x" 0.25 (0.65 typ) (5.65) (0.35 typ) (1.45) 6.40 4.40 0.10 0.65 1.20 max pin #1 i.d. mark 9.70 0.10 -0.06 0.15 +0.05 -0.10 +0.15 -0.06 +0.05 0.20 c b a 0.10 c - 0.05 0.10 c b a m

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